RobustPCBWhere Robust Design Starts
الحاسباتEnglishUpgradeتسجيل الدخولإنشاء حساب

ما الجديد

سجل التغييرات الكاملالمحرّك 1.26.4

Buck Converter Design

Power & Regulators

Inductor and output capacitor for a synchronous buck, with the current waveform.

هذه الصفحة غير مترجمة بالكامل بعد. الأجزاء غير المترجمة معروضة بالإنجليزية.

المدخلات

V
V
A
Hz
500 kHz
H
10 µH
ΔIL as % of Iout. 20–40 % is typical.
%
F
44 µF
ESR and efficiency
Ω
5 mΩ
%

النتائج

1 ناجحة
Suggested L for 30 % ripple
8.861µH
ناجح

المعيار: your 10 µH inductor against the 8.861 µH needed for 30 % ripple at 2 A
أظهر خطوات الحساب
  1. Duty cycleD = V_out / (V_in × η) = 3.3 / (12 × 0.9) = 30.6 %
  2. Inductor ripple currentΔI_L = (V_in − V_out) × D / (L × f_sw) = 8.7 × 0.3056 / (10 µH × 500 kHz) = 531.7 mA
  3. Inductor for 30 % rippleL = (V_in − V_out) × D / (f_sw × I_out × 0.3) = 8.7 × 0.3056 / (500 kHz × 2 × 0.3) = 8.861 µH
  4. Peak inductor currentI_pk = I_out + ΔI_L / 2 = 2 + 532 mA / 2 = 2.266 A
Inductor ripple ΔIL
531.7mA
Peak inductor current Ipk

Isat ≥ 2.719 A (+20 %) at temperature
2.266A
Output ripple ΔVout
5.679mV
كل النتائج (6)
Duty cycle D

at 90 % efficiency
30.6%
Inductor RMS current
Average input current Iin
611.1mA
Cin RMS current
DCM boundary
Loss at this efficiency
733.3mW
iL(t)

إلى أي حد نعرف هذا الرقم

مدى دقتها
Ideal-switch relations, exact for the assumed waveform.

They ignore dead time, switch drops and the inductance lost near saturation, so expect more ripple than this and check the inductor curve at your peak current.

عملياً يهيمن على عدم اليقين مدخل واحد: Inductor. ضيّقه يضِق معه الجواب.

هذه أداة مساعدة للتصميم. يبقى المهندس مسؤولاً عن التصميم وعن قراءة المرجع القياسي نفسه حيث يهم ذلك.

المسح البارامتري

غيّر مدخلاً واحداً على مدى، وشاهد الإجابة والحكم والهامش عند كل خطوة، جدولاً ومنحنى.Pro

أسوأ الحالات

أضف التفاوتات إلى المدخلات لتحصل على النطاق المضمون حول الإجابة الاسمية، لا الحالة النموذجية وحدها.Pro

Circuit

المبدأ

A buck converter switches one end of an inductor between Vin and ground. In steady state the inductor's volt-seconds balance over each cycle, and that gives the duty cycle, the ripple and the component ratings.

Volt-second balance → duty cycle
(Vin−Vout) ton=Vout toff  ⇒  D=VoutVin(V_{in}-V_{out})\,t_{on} = V_{out}\,t_{off} \;\Rightarrow\; D = \frac{V_{out}}{V_{in}}
With losses, D ≈ Vout /(η·Vin): a little more on-time makes up the loss.
Inductor ripple current
ΔIL=(Vin−Vout) DL fsw=Vout(1−D)L fsw\Delta I_L = \frac{(V_{in}-V_{out})\,D}{L\,f_{sw}} = \frac{V_{out}(1-D)}{L\,f_{sw}}
Inductor selection for a target ripple ratio r
L=(Vin−Vout) Dfsw r IoutL = \frac{(V_{in}-V_{out})\,D}{f_{sw}\, r\, I_{out}}
r = ΔIL / Iout. r ≈ 0.3 balances inductor size, RMS loss and transient response.
Peak and RMS inductor current
Ipk=Iout+ΔIL2IL,rms=Iout2+ΔIL212I_{pk} = I_{out} + \frac{\Delta I_L}{2} \qquad I_{L,rms} = \sqrt{I_{out}^{2} + \frac{\Delta I_L^{2}}{12}}
Output voltage ripple
ΔVout=ΔIL8 Cout fsw+ΔIL⋅ESR\Delta V_{out} = \frac{\Delta I_L}{8\,C_{out}\,f_{sw}} + \Delta I_L \cdot ESR
Capacitive term plus ESR term. Ceramics: the first dominates. Electrolytics and polymers: usually the ESR term.
Input capacitor RMS current
ICin,rms=IoutD(1−D)I_{C_{in},rms} = I_{out}\sqrt{D(1-D)}
Largest at D = 0.5, where it is Iout/2. It sets input capacitor heating and life.
CCM / DCM boundary
Iout,crit=ΔIL2I_{out,crit} = \frac{\Delta I_L}{2}
  • DDduty cycle of the high-side switch
  • ΔIL\Delta I_Lpeak-to-peak inductor ripple current
  • fswf_{sw}switching frequency
  • ESRESRequivalent series resistance of the whole output capacitor bank
  • η\etaefficiency at this operating point
تفاصيل إضافية

Switching frequency

Higher fsw shrinks L and C, but switching and gate-drive loss rise in proportion and EMI gets harder to control. 300–600 kHz is common for general power and 1–2 MHz where size matters. Automotive designs often run near 2.2 MHz to stay clear of the AM broadcast band (up to about 1.7 MHz).

Layout

The hot loop. Input capacitor → high-side FET → low-side FET → back to the capacitor. Its area sets radiated EMI and switch-node ringing: make it as small as possible, on one layer, over an unbroken plane.
  • Keep the switch node copper small.
  • Route the feedback trace away from the switch node and inductor, referenced to the output capacitor's ground.
  • Use the capacitance left after DC-bias derating: a 22 µF X5R 0805 rated 6.3 V can be under 10 µF at 5 V.

Transient response. A load step ΔI dips the output by roughly ΔI·tresponse/Cout, with tresponse set by the loop bandwidth. To reduce the dip, add capacitance or bandwidth, not inductance.

Related: MOSFET Loss Budget for the switch, Decoupling & Bulk Capacitance for the load side, Trace Width for the power path.

إصدار المحرك ⁨1.26.4⁩